Sensorless control systems and methods for permanent magnet rotating machines

ABSTRACT

Systems and methods for controlling a rotating electromagnetic machine. The rotating machine, such as a permanent magnet motor or hybrid switched reluctance motor, includes a stator having a plurality of phase windings and a rotor that rotates relative to the stator. A drive is connected to the phase windings for energizing the windings. A controller outputs a control signal to the drive in response to an input demand such as a demanded speed or torque. Control methods (which can be implemented separately or in combination) include varying the gain of an estimator as a function of a demanded or estimated speed to position control system poles at desired locations, de-coupling control system currents to achieve a constant torque with motor speed, compensating flux estimates of the estimator for saturation operation of the stator, estimating rotor position using averages of sample values of energization feedback, and calculating a trim adjusted speed error from a plurality of speed estimates.

CROSS-REFERENCE TO RELATED APPLICATIONS

This application is a divisional of U.S. application Ser. No. 11/293,744filed Dec. 2, 2005, and claims the benefit of U.S. ProvisionalApplications No. 60/694,077 and No. 60/694,066 filed Jun. 24, 2005. Theentire disclosures of the above applications are incorporated herein byreference.

FIELD

The present disclosure relates generally to control of rotatingmachines, including but not limited to sensorless control of permanentmagnet rotating machines.

BACKGROUND

Permanent magnet machines, such as brushless permanent magnet motors,have been conventionally provided with position sensing devices. Suchdevices indicate, for use in controlling the motor, the rotor positionwith respect to the stator. However, rotor position sensors can be quiteexpensive, occupy space within a motor housing, and sometimes fail. Toeliminate the need for position sensors, various “sensorless” motorconstructions and methods have been developed with varying degrees ofsuccess. As recognized by the present inventors a need exists forimprovements in sensorless control systems for rotating permanent magnetmachines.

SUMMARY

According to one aspect of the present disclosure, a method is providedfor estimating rotor position in a sensorless control system for apermanent magnet rotating machine. The machine includes a stator and arotor situated to rotate relative to the stator. The stator has aplurality of energizable phase windings situated therein. The methodincludes sampling energization feedback from the machine to obtain aplurality of samples, averaging a pair of the plurality of samples toproduce an average sample value, and estimating the rotor position usingthe average sample value.

According to another aspect of the present disclosure, a method isprovided for controlling a permanent magnet rotating machine. Themachine includes a stator and a rotor situated to rotate relative to thestator. The stator has a plurality of energizable phase windingssituated therein. The method includes producing a first rotor speedestimate, producing a second rotor speed estimate, and calculating atrim-adjusted speed error using the first rotor speed estimate and thesecond rotor speed estimate.

Further aspects of the present disclosure will be in part apparent andin part pointed out below. It should be understood that various aspectsof this disclosure may where suitable be implemented individually or incombination with one another. It should also be understood that thedetailed description and drawings, while indicating certain exemplaryembodiments, are intended for purposes of illustration only and shouldnot be construed as limiting the scope of this disclosure.

BRIEF DESCRIPTION OF THE DRAWINGS

FIG. 1 is a block diagram of a rotating permanent magnet (PM) machinesystem according to one exemplary embodiment of this disclosure.

FIG. 2 is a block diagram of a PM machine system configured to operateprimarily in a torque control mode according to another exemplaryembodiment of this disclosure.

FIG. 3 is a block diagram of a PM machine system configured to operateprimarily in a speed control mode according to another exemplaryembodiment.

FIG. 4 is a graph illustrating how gain values can be varied withrespect to rotor speed so as to maintain the poles of an observeremployed by the estimators of FIGS. 2 and 3 in desired locations.

FIGS. 5 a and 5 b illustrate how estimator gain values approachexcessive values as the rotor speed approaches zero.

FIG. 6 is a block diagram illustrating how estimator gain values can bestored in and accessed from lookup tables.

FIG. 7 is a flow diagram of a method implemented by the gain schedulersof FIGS. 2 and 3 according to another exemplary embodiment.

FIG. 8 is a flow diagram of a method of calculating a Qr-axis currentbased on a given dr-axis current injection to produce a desired rotortorque according to another exemplary embodiment.

FIG. 9 is a block diagram of a speed loop controller, a torque to IQdrMap block, and a Idr injection block according to another exemplaryembodiment.

FIG. 10 is a block diagram of the torque and Idr to IQr map block ofFIG. 9 according to another exemplary embodiment.

FIG. 11 is a block diagram illustrating how saturation effects can becompensated for in the measurement path of an observer according toanother exemplary embodiment.

FIG. 12( a) is graph illustrating how two energization feedback samplesare collected at the beginning and end of an exemplary sampling intervalaccording to the prior art.

FIG. 12( b) is a graph illustrating how two energization feedbacksamples can be collected and averaged to produce an estimated rotorposition/angle according to another embodiment of this disclosure.

FIG. 13 is a block diagram of an exemplary speed trim mechanism forproducing a speed trim value that can be provided to the estimator ofFIG. 3 according to another exemplary embodiment of this disclosure.

Like reference symbols indicate like elements or features throughout thedrawings.

DETAILED DESCRIPTION OF EXEMPLARY EMBODIMENTS

Illustrative embodiments are described below. In the interest ofclarity, not all features of an actual implementation are described inthis specification. It will be appreciated that in the development ofany actual embodiment, numerous implementation-specific decisions mustbe made to achieve specific goals, such as performance objectives andcompliance with system-related, business-related and/or environmentalconstraints. Moreover, it will be appreciated that such developmentefforts may be complex and time-consuming, but would nevertheless be aroutine undertaking for those of ordinary skill in the art having thebenefit of this disclosure.

FIG. 1 illustrates a rotating permanent magnet machine system 100according to one embodiment of the present disclosure. The machinesystem 100 includes a rotating permanent magnet electric machine 101,such as a permanent magnet alternating current (PMAC) motor or a hybridpermanent magnet/switched reluctance (PM/SR) motor. For simplicity, theterm “motor” is often used in this specification. However, one skilledin the art having the benefit of this disclosure will understand that itis applicable to other types of rotating electric machines, includinggenerators. The PM machine 101 shown in FIG. 1 includes a stationarycomponent (stator) 102 and a rotating component (rotor) 104. The machine101 can have an inner rotor or an outer rotor construction. In thisexemplary embodiment, the PM machine 101 is a three phase machine havingan inner rotor construction with energizable phase windings 106A, 106B,106C wound about the stator 102, which are energized through theapplication of electric power to the motor terminals.

A drive 108 is coupled to the terminals of the machine for providingelectric power. The drive 108 receives control inputs from a controller110 that receives energization feedback 112 from the machine (such asthe currents and/or voltages at the motor terminals), or that assumesthe actual voltage supplied to the motor is that which was demanded bythe controller 110 (e.g., in the form of PWM duty cycle), from which theelectrical angle and electrical speed can be determined (i.e., estimatedsensorlessly). From these estimates, rotor speed can be inferred, as canrotor angle (to the extent the estimates are based upon electricalangle). The controller 110 of FIG. 1 is shown as receiving an inputdemand 114 that may be, for example, a torque demand or a speed demand.

While the drive 108 of FIG. 1 is illustrated in exemplary form asenergizing three power terminals of a three phase machine 101, it shouldbe understood that more or fewer power terminals may be provided toaccommodate machines with greater or less than three phases, or ifvarious types of inverters (e.g., with neutral connections) are used.The drive may be of conventional design and configured to provide, forexample, sine wave excitation to the motor terminals or square waveexcitation using conventional pulse width modulation (PWM) excitation.

FIG. 2 illustrates additional details of the system of FIG. 1 asconfigured to operate primarily in a torque control mode. For thisreason, a torque demand input 214 is shown in FIG. 2. The torque demandinput may be received directly by the system 200 as an external commandor alternatively, may be derived from an external command. For example,the torque demand input may be derived from a speed demand input or froman air flow demand input (e.g., where the system of FIG. 2 is embodiedin an air handler/blower for a climate control system). Additionaldetails regarding the embodiment of FIG. 2 are provided in U.S.Application No. [Docket No. 5260-000211/US filed on Dec. 2, 2005] titledControl Systems and Methods for Permanent Magnet Rotating Machines andfiled [on even date herewith], the entire disclosure of which isincorporated herein by reference.

FIG. 3 illustrates additional details of the system of FIG. 1 asconfigured to operate primarily in a speed control mode. Furtherinformation regarding operating in speed control modes is set forth inU.S. Pat. No. 6,756,753.

Described below are several additional improvements in controlling a PMmachine according to various aspects of the present disclosure. Itshould be understood that each improvement can be advantageouslyimplemented by itself or in combination with one or more otherimprovements disclosed herein.

As shown in FIGS. 2 and 3, the controller of FIG. 1 can include anestimator 202, 302 for estimating the machine's electrical speed andangle. In some embodiments, the estimators 202, 302 employ a LuenbergerObserver. However, other types of observers, including the KalmanEstimator, may be employed.

According to one aspect of the present disclosure, the gain of anestimator—such as the estimators 202, 302 shown in FIGS. 2 and 3—can bevaried (e.g., using the gain schedulers 204, 304 shown in FIGS. 2 and 3)as a function of either a demanded rotor speed (including a filtereddemanded speed) or an estimated rotor speed. In this manner, controlsystem poles (i.e., poles of the observer) can be positioned at desiredlocations, including maintaining the poles at desired and notnecessarily fixed locations to improve control system and machinestability.

In a torque control mode of operation, there is no demanded speed.Therefore, the estimator gains are preferably varied as a function ofthe estimated rotor speed so as to position the control system poles atdesired locations. The estimated rotor speed used in the gain schedulingmay be pre-processed in a suitable manner before being used in the gainscheduling scheme, typically being passed through a low pass filter.

In one embodiment of a speed control mode of operation, the polelocations of the estimators 202, 302 are increased as speed increases,with the slowest pole locations occurring as the system is switched fromopen loop operation to closed loop operation.

The gain values can be calculated for a range of speeds. This may bedone on the fly by the gain scheduler 204, 304 of FIG. 2 or 3 using aclosed form set of equations. Alternatively, the gain values may beretrieved by the gain scheduler from one or more look-up tables or froma fitted curves characterizing the gain-speed profile for a specificmotor.

FIG. 4 illustrates how gain values are varied with respect to theelectrical speed in one exemplary embodiment so as to maintain observerpoles at desired locations.

FIGS. 5 a and 5 b illustrate how gain values approach excessive valuesas the electrical speed approaches zero. For this reason, gain valuesare preferably not calculated as described within a range of valuesaround zero electrical speed. At low or zero speeds, predetermined gainvalues which are sufficiently high, but not excessive, are preferablyused, thereby improving control system stability.

FIG. 6 illustrates how gain values may be stored in and accessed fromlookup tables. In the particular embodiment of FIG. 6, two columns ofgain values are constructed through a multiplexer and then concatenatedtogether to form a 4×2 gain matrix.

FIG. 7 is a flow diagram 700 illustrating one preferred implementationof the gain schedulers 204, 304 of FIGS. 2 and 3 in which the speed usedby the gain scheduler, referred to as the scheduled speed, is set to thedrive speed (i.e., a demanded rotor speed) at lower rotor speeds and tothe estimated electrical speed at higher rotor speeds.

In step 702, the controller transforms state variables into a rotatingframe of reference. In step 704, the controller reads the estimatedelectrical speed and then reads the drive speed (i.e., the demandedspeed) in step 706. In step 708, the controller compares the drive speedto a predetermined threshold speed. The predetermined speed thresholdparameter can be selected, as needed, for any given PM machine.

If the drive speed is greater than the predetermined threshold speed,the scheduled speed used by the gain schedulers 204, 304 (FIGS. 2 and 3)is set equal to the estimated electrical speed in step 710. If the drivespeed is less than the predetermined threshold speed, the scheduledspeed used by the gain schedulers 204, 304 is set equal to the drivespeed in step 712. Subsequent to controller selection of the appropriatescheduled speed, the selected schedule speed is used by gain schedulers204, 304 to look up or calculate the estimator gains in step 714 tomaintain the system poles at desired positions. The estimator uses thescheduled gain factors and the updated observer states in step 716 tocalculate an updated estimated electrical angle in step 718 and anupdated estimated electrical speed in step 720. The updated electricalspeed estimate is filtered in step 722 and the filtered speed estimateis integrated in step 724 to produce an updated electrical angle demand.

According to another aspect of the present disclosure, a Qr-axis currentcan be selected that, in conjunction with a given value of dr-axiscurrent, will produce a desired rotor torque. This aspect isparticularly well suited to hybrid PM/SR motors, where the dr-axiscurrent component contributes to the amount of torque produced, andespecially hybrid PM/SR motors employing a dr-axis injection current.

FIG. 8 is a flow diagram 800 illustrating a method of calculating aQr-axis current based on a given dr-axis current injection to produce adesired rotor torque according to one exemplary embodiment. In thisembodiment, the dr-axis current injection is calculated off-line inaccordance with a dr-axis current injection method described inco-pending U.S. Application [Docket 5260-000211/US filed on even dateherewith] noted above. These values are typically stored in a lookuptable but may also be described as a mathematical function inalternative embodiments. The motor speed and the value of the dc-linkare used to calculate the value of the dr-axis injection current to beapplied at any given moment in time.

In step 802, the controller reads the demanded electrical speed 802 andthen reads the estimated electrical speed in step 804. In step 806, thecontroller calculates a speed error. The controller uses the calculatedspeed error from step 806 to update the control action in step 808.After updating the control action, the controller reads the intendeddr-axis injection current in step 810, calculates the Qr-axis currentrequired to produce a demanded torque in step 812 and outputs thedemanded Qr- and dr-axis currents in step 814 to a pair of currentcontrollers, such as current controllers 206, 208 of FIG. 2 or currentcontrollers 306, 308 of FIG. 3.

FIG. 9 is a block diagram of a speed loop controller 902, a torque toIQdr Map block 904, and a Idr injection block 906 according to anotherexemplary embodiment. As shown in FIG. 9, the selected Qr-axis currentand the dr-axis injection current are multiplexed and provided to a pairof current controllers, preferably as a multiplexed demand signal, IQdrdemand 908. In this embodiment of the Idr injection block 906, therequired Idr current is calculated from the speed error, assuming thatIdr is for the moment nominally zero.

FIG. 10 is a block diagram of the Torque and Idr to IQr map block ofFIG. 9 according to another exemplary embodiment of this disclosure. Inthis embodiment, using the motor-specific constants noted, theIqr_demand is calculated as:

Iqr_demand=(54.5*Torque demand+0.4373*Idr)/(22.54−Idr)

The decoupling of IQdr components in the production of torque can beapplied within either a sensorless control system or a sensor-controlledsystem. If a given motor does not show any discernible hybrid behavior,the control technique can default to that classically used with a PMmotor (i.e., Idr torque contribution is assumed to be zero) where thetorque contribution comes from IQr.

According to another aspect of this disclosure, the flux estimateproduced by a flux estimator 202, 302, such as the estimators shown inFIGS. 2 and 3, can be compensated for saturation effects when the motoroperates in the nonlinear saturation regions of stator magnetic flux. Inthis manner, errors in the flux estimate can be reduced, thus reducingerrors in rotor position and/or rotor speed estimates produced from theflux estimate. As a result, the stability of the control system isimproved under stator saturation operating conditions. This improvementis particularly important when the structure of the drive control isbased upon manipulating variables generated using transformations havingvalues dependent on the machine electrical angle. This aspect of thedisclosure is particular well suited for hybrid PM machines, PM machineshaving embedded rotor magnets, and PM machines employing highlymagnetized material.

The compensated flux estimate can be produced using nonlinear correctionterms including, for example, dominant angle invariant terms associatedwith saturation, including cubic terms. Dominant angle-varying terms mayalso be used to produce the compensated flux estimate. Terms may also bepresent that include quadratic current expressions when they have adominant effect on the flux estimate. In one embodiment of thisdisclosure directed to an air handler for a climate control system, thedominant terms are cubic.

In one exemplary embodiment, a flux estimate is first produced usingenergization feedback 112 from the machine. This flux estimate is thencompensated for saturation effects, with the flux estimate becomingsignificant as the saturation effects themselves become significant

FIG. 11 is a block diagram illustrating how saturation effects arecompensated for in the measurement path of an Observer (e.g., embodiedin a flux estimator) according to one exemplary embodiment of thisdisclosure. When the controller detects saturation operation of thestator, the compensated flux estimate is used by the estimator toestimate rotor speed and rotor position.

According to another aspect of the present disclosure, a rotor position(i.e., angle) estimator—such as the estimators 202, 302 shown in FIGS. 2and 3—can average samples of the energization feedback 112 from themachine and estimate the rotor position using the average sample values.In this manner, the magnitude of the potential error within eachsampling interval is reduced in half, resulting in more accurate controlof the machine when control of the machine is dependent on accuratelyestimating the rotor position. Although the magnitude of the potentialerror within each sampling interval increases as the sampling ratedecreases, it should be understood that this aspect of the presentdisclosure can be advantageously used with any sampling rate to improvethe accuracy of the estimated rotor position. The estimate calculationeffectively compensates for time delays resulting from use of the angleestimate in the drive.

Preferably, each successive pair of samples (including the second samplefrom the immediately preceding successive sample pair) is averaged toproduce a series of average sample values which are used to estimate therotor position.

FIG. 12( a) illustrates how two samples are collected at the beginningand end of an exemplary sampling interval according to the prior art,where each sample is treated as representing the actual rotorposition/angle at the time such sample was obtained. FIG. 12( b)illustrates how two samples are collected and averaged to produce anestimated rotor position/angle. Collectively, FIGS. 12( a) and 12(b)illustrate that while the range of error (2 e) remains the same, theabsolute value of the potential error about the average angle estimatein FIG. 12( b) is reduced in half (+/−e) as compared to FIG. 12( a),where the angle error estimate could be as large as 2 e.

According to another aspect of the present disclosure, a trim-adjustedspeed error can be calculated and provided, e.g., to a speedcontroller—such as the speed controller shown in FIG. 3. An exemplarymethod includes producing a first rotor speed estimate, producing asecond rotor speed estimate, and calculating a trim-adjusted speed errorusing the first rotor speed estimate and the second rotor speedestimate. Preferably, a trim value is produced by calculating adifference between the first rotor speed estimate and the second rotorspeed estimate. Additionally, a raw speed error is preferably producedby calculating a difference between a demanded rotor speed and anestimated rotor speed (which may be the first rotor speed estimate orthe second rotor speed estimate, and preferably the more reliable one ofsuch estimates, which may depend, e.g., on the PWM rate of the motordrive). The trim-adjusted speed error is preferably calculated by addingthe trim value to the raw speed error.

The first rotor speed estimate can be produced using modeled motorparameters, and the second rotor speed estimate can be produced usingzero crossings detected from energization feedback from the machine. Inthis manner, the trim value and thus the trim-adjusted speed error canaccount for potential variations between modeled motor parameters andactual parameters of a production motor.

FIG. 13 is a block diagram of an exemplary trim mechanism for producinga trim value that can be provided, e.g., to an estimator such as theestimator shown in FIG. 3. In this embodiment, the trim error 1302 isfiltered using a first order low pass filter 1304. The filtered trimerror signal 1306 is then added directly to the error signal driving thespeed loop controller. FIG. 9, discussed above, illustrates an exemplaryspeed controller that includes an input 910 for such a trim value. Thetrim mechanism can be used to improve the performance of anestimator-based sensorless control system.

1. A method of estimating rotor position in a sensorless control systemfor a permanent magnet rotating machine, the machine including a statorand a rotor situated to rotate relative to the stator, the stator havinga plurality of energizable phase windings situated therein, the methodcomprising: sampling energization feedback from the machine to obtain aplurality of samples; averaging a pair of the plurality of samples toproduce an average sample value; and estimating the rotor position usingthe average sample value.
 2. The method of claim 1 wherein averagingincludes averaging a successive pair of the plurality of samples.
 3. Themethod of claim 1 wherein averaging includes averaging each successivepair of the plurality of samples to produce a plurality of averagesample values, and estimating includes estimating the rotor positionusing the plurality of average sample values.
 4. A permanent magnetrotating machine and controller assembly configured to perform themethod of claim
 1. 5. A climate control system comprising the assemblyof claim
 4. 6. The climate control system of claim 5 wherein the systemincludes an air handler and wherein the air handler includes saidassembly.
 7. A method of controlling a permanent magnet rotatingmachine, the machine including a stator and a rotor situated to rotaterelative to the stator, the stator having a plurality of energizablephase windings situated therein, the method comprising: producing afirst rotor speed estimate; producing a second rotor speed estimate; andcalculating a trim-adjusted speed error using the first rotor speedestimate and the second rotor speed estimate.
 8. The method of claim 7wherein calculating includes producing a trim value by calculating adifference between the first rotor speed estimate and the second rotorspeed estimate.
 9. The method of claim 8 wherein calculating furtherincludes producing a raw speed error by calculating a difference betweena demanded rotor speed and an estimated rotor speed.
 10. The method ofclaim 9 wherein calculating further includes adding the trim value or afiltered trim value to the raw speed error.
 11. The method of claim 7wherein the first rotor speed estimate is produced using modeled motorparameters.
 12. The method of claim 11 wherein the second rotor speedestimate is produced using zero crossings detected from energizationfeedback from the machine.